Receiver for a telecommunication system

ABSTRACT

A receiver is described, the receiver comprising an ABB filter stage, an ADC stage. The ABB filter stage comprises an ABB filter stage input configured to receive an analog baseband, BB, signal and an ABB filter stage output configured to provide a filtered analog BB signal. The ADC stage comprises an ADC stage input configured to receive the filtered analog BB signal and an ADC stage output configured to provide a digital BB signal. The ADC stage comprises an ADC comprising an ADC input configured to receive the filtered analog BB signal or a signal derived therefrom as an ADC input signal, and wherein the ADC is configured to perform an analog-to-digital, A/D, conversion of the ADC input signal to derive the digital BB signal.

CROSS-REFERENCE TO RELATED APPLICATIONS

This application is a continuation of U.S. patent application Ser. No.16/392,899, filed on Apr. 24, 2019, which is a continuation ofInternational Application No. PCT/EP2016/075688, filed on Oct. 25, 2016.All of the afore-mentioned patent applications are hereby incorporatedby reference in their entireties.

TECHNICAL FIELD

The present application relates to a receiver for a telecommunicationssystem.

BACKGROUND

The bandwidth of the radio channel in telecommunications systems isgetting wider and wider, from hundreds of kilohertz range in 2 G to tensor even hundreds of megahertz range in 4.5 G and 5 G. This increase inbandwidth requires an ever increasing flexibility especially for radioreceiver baseband filtering prior to analogue-to-digital conversion.Furthermore, the receiver silicon area and current consumption should beminimized as more and more receivers have to be integrated on the samechip to support diversity, Multiple Input Multiple Output, MIMO, andcarrier aggregation requirements in 4 G and 5 G.

In order to tackle the area and power reduction requirements, severalsolutions of merging filtering and continuous-time delta-sigmaanalogue-to-digital converters (ΔΣ ADCs) have been published in recentyears.

With present solutions, a feedback digital-to-analog converter DACinjects its signal at the same point where a down converted and almostunfiltered radio frequency, RF, signal is injected. This leads to verylow clock jitter specifications thus increasing power consumption andsilicon area for the clock generation and distribution.

The main problem with the present solutions for filtering ADCs is thatthey do not solve the right problem. The present solutions present anenergy efficient solution in the medium frequency range (5 . . . 20MHz), but for wider bandwidths the frequency and phase response of themain ADC affects the total filtering response thus rendering the designvery difficult and increasing current consumption. On the other hand, atnarrower bandwidths, there is already enough noise shaping in the mainADC so that noise shaping boost of the merged filter is not required.

Another problem with the current solutions is the limited usability withvery wide filter bandwidths in respect to the ADC sampling frequencyi.e. with low oversampling ratio, OSR.

SUMMARY OF THE APPLICATION

An objective of embodiments of the present application is to provide areceiver which at least diminishes the problems with conventionalsolutions.

Another objective of the present application is to provide a receiverwhich enables minimization of silicon area and power consumption in thereceiver while maintaining the filtering performance.

The above objectives are fulfilled by the subject matter of theindependent claim. Further advantageous implementation forms of thepresent application can be found in the dependent claims.

According to a first aspect of the present application a receiver isprovided comprising: an analog baseband, ABB, filter stage, ananalog-to-digital converter, ADC, stage, a first feedback path, and asecond feedback path; wherein the ABB filter stage comprises an ABBfilter stage input configured to receive an analog baseband, BB, signaland an ABB filter stage output configured to provide a filtered analogBB signal; wherein the ADC stage comprises an ADC stage input configuredto receive the filtered analog BB signal and an ADC stage outputconfigured to provide a digital BB signal; wherein the ADC stagecomprises an ADC comprising an ADC input configured to receive thefiltered analog BB signal or a signal derived therefrom as an ADC inputsignal, and wherein the ADC is configured to perform ananalog-to-digital, A/D, conversion of the ADC input signal to derive thedigital BB signal; wherein the first feedback path is configured tofeedback the ADC input signal to the ABB filter stage; wherein thesecond feedback path is configured to feedback the digital BB signal tothe ABB filter stage.

The receiver according to the first aspect enables minimization of thesilicon area and power consumption. This is due to the fact that thereceiver according to the first aspect enables sharing of circuitrybetween the ABB filter stage and the ADC, which also relaxes the ADCspecification, therefore saves area and power.

The receiver according to the first aspect enables elimination of thefirst feedback DAC thus relaxing clock jitter requirements whilemaintaining enough noise shaping for the ADC quantization noise.

The receiver according to the first aspect can reach very low OSR evenbelow 4. This can be achieved by using first-order CT ΔΣ ADC or even aNyquist ADC as the main ADC.

In order to minimize silicon area and power consumption, the analoguebaseband filter and analogue-to-digital converter should share as muchcircuitry as possible. This is achieved according to the first aspect ofthe application by merging and sharing of the integrator stages of theABB, filter stage and the ADC, stage.

The power consumption and silicon area is also kept low for narrowerbandwidth radio standards due to the use of fewer integrator stages.Part of the filtering ADC dynamic range can be traded off to betterfrequency selectivity by adding deliberate digital delay in the feedbackDAC path. With this method, the filter order is increased by one in themost crucial area just above the low pass filter corner frequency.

In one embodiment, the first feedback path is analog. The analogfeedback path stabilizes filter frequency response peaking around thefilter corner frequency and thus relaxes unity gain frequencyspecification of the filter operational amplifier.

In one embodiment, the second feedback path comprises a first feedbackdigital-to-analog, D/A, converter. The inclusion of a D/A converter inthe second feedback path enables a proper feedback from the digital BBsignal to the ABB filter stage. The second feedback path also lowers thefilter sensitivity. This saves power in the widest bandwidth modes.

In one embodiment, the second feedback path comprises a delay element.By adding a delay element fourth order lowpass filtering is achievedclose the corner frequency. At higher frequencies the filter falls backto third order lowpass slope. This method improves receiver frequencyselectivity at the expense of slightly decreased SNR. The added delayshifts noise transfer function, NTF, notch down in frequency. Thecorrect notch frequency can be restored with an additional weakerfeedback path from quantizer input to the second integrator input.

In one embodiment the ABB filter stage comprises a first summation node,a first integrator, a second summation node and a second integrator;wherein the first summation node is configured to receive the analog BBsignal and to provide a first sum signal to the first integrator;wherein the first integrator is configured to integrate the first sumsignal to derive a first integrated signal; wherein the second summationnode is configured to receive the first integrated signal and to providea second sum signal to the second integrator; wherein the secondintegrator is configured to integrate the second sum signal to derivethe filtered analog BB signal; wherein each summation node is configuredto also receive the signal from one of the first feedback path and thesecond feedback path; and wherein each summation node is configured tosum the signals input to the respective summation node. The merged ABBand ADC performs third order low pass filtering for the received signal.The merged ABB shapes ADC quantization noise by adding a notch slightlybelow the low pass filter corner frequency. This is a very usefulfeature for optimizing wideband SNR of the ADC.

In one embodiment, the first summation node is configured to receive thesignal from the first feedback path and the second summation node isconfigured to receive the signal from the second feedback path. Thisfurther enhances the merge of the ABB and the ADC.

In one embodiment, the ADC stage comprises a third integrator coupledbetween the ADC stage input and the ADC input.

In one embodiment, the ADC stage comprises a third summation node at theADC stage input and a third feedback path, wherein the third feedbackpath is configured to feed back the digital BB signal to the thirdsummation node, wherein the third feedback path comprises a secondfeedback D/A converter, and wherein the third summation node isconfigured to sum the signal from the third feedback path and thefiltered analog BB signal and to provide a resulting third sum signal tothe third integrator.

In one embodiment, the ABB filter stage comprises a fourth feedback pathconnected between the first integrator output of the first integratorand the first summation node. The fourth feedback path enables settingof the gain in the filter. This makes it possible to adapt the receiverto the received analog BB signals.

In one embodiment, a fifth feedback back path is configured to feedbackthe filtered analog BB signal to the first summation node. This fifthfeedback enables further setting of the gain of the receiver. This makesit possible to adapt the receiver to the received analog BB signals.

In one embodiment, the fifth feedback path is analog. This isadvantageous as the filtered analog BB signal is an analog signal thatis to be fed back to an analog summation node.

In one embodiment, at least one of the first feedback path, the secondfeedback path, the third feedback path, the fourth feedback path, andthe fifth feedback path is switchable. By having at least one of thefirst feedback path, the second feedback path, the third feedback path,the fourth feedback path, and the fifth feedback path switchable it ispossible to adapt the receiver to different analog BB signals.

In one embodiment, the receiver is configured to selectively switch onand switch off the first to fifth feedback path in dependence on thesignal type of the received analog BB signal. By having the receiverconfigured in this way it is possible for the receiver to adapt itselfto different analog BB signals.

According to a second aspect of the present application a communicationdevice for a wireless communication system is provided, wherein thecommunication device comprises a receiver according to anyone of thefirst to the thirteenth implementation forms of the receiver or to thefirst aspect as such. Such a communication device has all the benefitsas described above for the different implementation forms of thereceiver or of the first aspect.

BRIEF DESCRIPTION OF THE DRAWINGS

FIG. 1 shows a receiver according to an embodiment of the application.

FIG. 2 shows a receiver according to another embodiment of theapplication.

FIG. 3 shows a receiver according to another embodiment of theapplication.

FIG. 4 shows a receiver according to another embodiment of theapplication.

FIG. 5 shows schematically a communication device in a wirelesscommunication system.

DETAILED DESCRIPTION

Below a description of embodiments will follow. In the followingdescription of embodiments similar features in the different embodimentswill be denoted with the same reference numeral.

FIG. 1 shows schematically a receiver 100 according to an embodiment ofthe application. The receiver 100 comprises an analog baseband, ABB,filter stage 101, an analog-to-digital converter, ADC, stage 103, afirst feedback path 123, and a second feedback path 125. The ABB filterstage 101 comprises an ABB filter stage input 105 configured to receivean analog baseband, BB, signal 107 and an ABB filter stage output 109configured to provide a filtered analog BB signal 111. The ADC stagecomprises an ADC stage input 113 configured to receive the filteredanalog BB signal 111 and an ADC stage output 115 configured to provide adigital BB signal 117. Thus, the ABB filter stage is merged with the ADCstage 103 through the first feedback path 123 and the second feedbackpath 125. The ADC stage 103 comprises an ADC 119 comprising an ADC input121 configured to receive the filtered analog BB signal 111 or a signalderived therefrom as an ADC input signal 151. Thus, there might beadditional components between the ADC stage input 113 and the ADC input121 as is indicated by the dotted line. Such additional components willbe described below with reference to the other embodiments. The ADC 119is configured to perform an analog-to-digital, A/D, conversion of theADC input signal 151 to derive the digital BB signal 117. The firstfeedback path 123 is configured to feedback the ADC input signal 151 tothe ABB filter stage 101. The first feedback path 123 is analog. Thesecond feedback path 125 is configured to feedback the digital BB signal117 to the ABB filter stage 101. Not shown in FIG. 1 as not essentialfor understanding the embodiments of the present application are an LNA(low noise amplifier) and a frequency mixer of the receiver 100.

FIG. 2 shows a receiver 100 according to another embodiment of theapplication. Only the differences between the embodiment described inFIG. 1 and the embodiment shown in FIG. 2 will be described. In FIG. 2the ABB filter stage 101 is shown to comprise a first summation node133, a first integrator 131, a second summation node 137 and a secondintegrator 135. The first summation node 133 is configured to receivethe analog BB signal 107. The first summation node is configured to alsoreceive the signal from the first feedback path 123. As is indicated bythe minus sign at the first feedback path close to the first summationnode 133 the signal from the first feedback path 123 is inverted beforeit is input to the first summation node 133. The first summation node133 is configured to sum the signals input to the first summation node133 into a first sum signal and to provide the second sum signal to thefirst integrator 131. The first integrator is configured to integratethe first sum signal to derive a first integrated signal.

The second summation node 137 is configured to receive the firstintegrated signal. The second summation node 137 is configured to alsoreceive the signal from second feedback path 125. As is indicated by theminus sign at the second feedback path close to the second summationnode 137 the signal from the second feedback path 125 is inverted beforeit is input to the second summation node 137. The second summation node137 is configured to sum the signals input to the second summation node137 into a second sum signal and to provide the second sum signal to thesecond integrator 135. The second integrator is configured to integratethe second sum signal to derive the filtered analog BB signal 111.

As is shown in FIG. 2 the second feedback path 125 comprises a firstfeedback digital-to-analog, D/A, converter 127. The function of thefirst feedback digital-to-analog, D/A, converter 127 is to convert thedigital BB signal 117, which is output on the ADC stage output 115, intoan analog signal to be input to the second summation node 137 afterhaving been inverted.

Also shown in FIG. 2 is an RF front end 157 configured to provide theanalog baseband, BB, signal 107. The RF front end 157 shown in FIG. 3 isonly one possible implementation of an RF front end. Otherimplementations would be possible too and are clear for a person skilledin the art. The first feedback path 123 is analog. In a very simpleimplementation the analog feedback paths described herein may beimplemented by resistors.

FIG. 3 shows a receiver 100 according to another embodiment of theapplication. Only the differences between the embodiment described inFIG. 2 and the embodiment shown in FIG. 3 will be described. The ADCstage 103 comprises a third integrator 139 coupled between the ADC stageinput 113 and the ADC input 121. The second feedback path 125 comprisesa delay element 129. By adding the delay element 129 fourth orderlowpass filtering is achieved close the corner frequency of the receiver100. The added delay element 129 shifts noise transfer function (NTF)notch down in frequency. However, the correct notch frequency isrestored by first feedback path 123 between the ADC input 121 and thesecond summation node 137. Furthermore, this first feedback 123 pathalso lowers the filter sensitivity to the limited unity gain frequenciesof the integrator Operational Amplifiers, thus saving power in thewidest bandwidth modes.

The ADC stage 103 in the receiver shown in FIG. 3 comprises a thirdsummation node 149 at the ADC stage input 113 and a third feedback path141, wherein the third feedback path 141 which is configured to feedback the digital BB signal 117 to the third summation node 149. Thethird feedback path 141 comprises a second feedback D/A converter 143.The third summation node 149 is configured to sum the signal from thethird feedback path 141 and the filtered analog BB signal 111 and toprovide a resulting third sum signal to the third integrator 139.

In FIG. 3 the first feedback path 123 is configured to feedback the ADCinput signal 151 to the second summation node 137. This is in contrastto the embodiment shown in FIG. 2 where the first feedback path 123 isconfigured to feedback the ADC input signal 151 to the first summationnode 133. In general the first feedback path 123 enables widestbandwidth with a low in-band ripple of the receiver.

The receiver 100 also comprises a fifth feedback path 153 between theoutput of the second integrator 135 and the first summation node 133.The fifth feedback path 153 is analog.

FIG. 4 shows a receiver 100 according to another embodiment of theapplication. Only the differences between the embodiment described inFIG. 3 and the embodiment shown in FIG. 4 will be described. The ABBfilter stage 101 comprises a fourth feedback path 145 connected betweenthe first integrator output 147 of the first integrator 131 and thefirst summation node 133. The receiver 100 also comprises a fifthfeedback back path 153 configured to feedback the filtered analog BBsignal 111 to the first summation node 133. The fifth feedback path 153is analog. The receiver 100 comprises a first switch S1 arranged in thefourth feedback path 145, a second switch S2 arranged in the fifthfeedback path 153, a third switch S3 arranged in the second feedbackpath, and a fourth switch S4 arranged in the first feedback path 123.The receiver 100 is configured to selectively switch on and switch offthe first to the fourth switches to thereby switch on and off thecorresponding feedback paths 123, 125, 145, 153, in dependence on thesignal type of the received analog BB signal. 14.

Below, a number of different configurations for the receiver will bedescribed and the benefits of the different configurations will bediscussed. Switch on means it is closed i.e. low impedance, a switch offmeans it is open, i.e. high impedance. N marks the number of delayscycles in the second feedback path 125.

S1& S2 on, S3 & S4 Off

-   -   This is a normal direct conversion mode with separate ABB and        ADC. This mode could be described as a legacy mode for test,        performance comparison etc.    -   S1 and S2 paths set the gain, i.e., the fourth feedback path 145        and the fifth feedback path 153.        S1 & S3 on, S2 & S4 off, no delay (N=0)    -   Local feedback is provided for first integrator for optimized        capacitance area for narrow bandwidth (e.g. below 2 MHz) and        moderate selectivity. Furthermore, a maximum SNR can be        achieved.    -   First order merged ABB and ADC STF and second order NTF.    -   S1 and S3 paths set the gain, i.e., the fourth feedback path 145        and the second feedback path 125.    -   As described above this is the preferable configuration when the        received analog BB signal is a 2 G signal.        S1, S3 & S4 on, S2 Off, N>=0    -   Local feedback for first integrator for optimized capacitance        area for narrow bandwidth and high selectivity.    -   The Feedback delay used to boost selectivity so that TX-leakage        is minimized. The    -   This mode is optimized for Optimized for a wider bandwidths        especially in FDD use cases. For example 3G, LTE (especially for        LTE modes with bandwidth of 5 MHz and 10 MHz).    -   More than first order merged ABB and ADC STF and second order        NTF with freely adjustable notch in the NTF.    -   S1 and S3 paths, i.e., the fourth feedback path 145 and the        second feedback path 125, set the gain, S4 path, i.e., the first        feedback path, sets the NTF notch. Hence, S4 is pushes one NTF        notch to higher frequencies for optimal SNR across the channel        bandwidth.    -   It should be mentioned that the delay is required only in        certain use cases since in certain 3 G and LTE bands TX and RX        are very close while in other case it may be very large (>100        MHz).        S2, S3 & S4 on, S1 off, N>1    -   Wide bandwidth and high selectivity.    -   More than second order merged ABB and ADC STF and freely        adjustable notch in the NTF (excluding passive RC-filter).    -   S2 and S3 paths, i.e., the fifth feedback path 153 and the        second feedback path 125, set the gain. S2 path sets the NTF        notch and S4 path adjusts it.        S2 and S3 on, S1 and S4 Off, No Delay (N=0)    -   This mode works for most LTE modes including intra-band        carrier-aggregation.    -   With fast enough Operational Amplifiers the best SNR can be        achieved.    -   In certain use FDD use cases S4 may be switched on too for the        notch tuning.        S2, S3 & S4 on, S1 Off, No Delay (N=0)    -   Widest bandwidth and normal selectivity.    -   Second order merged ABB and ADC STF and freely adjustable notch        in the NTF (excluding passive RC-filter).    -   S2 and S3 paths set the gain. S2 path sets the NTF notch and        weak S4 path adjusts filter high frequency response.

FIG. 5 shows schematically a communication device 300 in a wirelesscommunication system 200. The communication device 300 comprises areceiver 100 according to an embodiment of the application. The wirelesscommunication system 200 also comprises a network node 400 whichcomprises a receiver 100 according to an embodiment of the application.The dotted arrow A1 represents transmissions from the communicationdevice 300 to the network node 400, which are usually called uplinktransmissions. The full arrow A2 represents transmissions from thenetwork node 400 to the communication device 300, which are usuallycalled downlink transmissions.

The communication device 300 may be any of a User Equipment (UE) in LongTerm Evolution (LTE), mobile station (MS), wireless terminal or mobileterminal which is enabled to communicate wirelessly in a wirelesscommunication system, sometimes also referred to as a cellular radiosystem. The UE may further be referred to as mobile telephones, cellulartelephones, computer tablets or laptops with wireless capability. TheUEs in the present context may be, for example, portable,pocket-storable, hand-held, computer-comprised, or vehicle-mountedmobile devices, enabled to communicate voice or data, via the radioaccess network, with another entity, such as another receiver or aserver. The UE can be a Station (STA), which is any device that containsan IEEE 802.11-conformant Media Access Control (MAC) and Physical Layer(PHY) interface to the Wireless Medium (WM).

The radio network nodes may be of different classes such as, e.g., macroeNodeB, home eNodeB or pico base station, based on transmission powerand thereby also cell size. The radio network node can be a Station(STA), which is any device that contains an IEEE 802.11-conformant MediaAccess Control (MAC) and Physical Layer (PHY) interface to the WirelessMedium (WM).

The invention claimed is:
 1. A receiver, comprising: an analog baseband(ABB) filter stage including an ABB filter stage input configured toreceive an analog baseband (BB) signal and an ABB filter stage outputconfigured to provide a filtered analog BB signal; an analog-to-digitalconverter (ADC) stage, including: an ADC stage input configured toreceive the filtered analog BB signal and an ADC stage output configuredto provide a digital BB signal; and an ADC comprising an ADC inputconfigured to receive the filtered analog BB signal or a signal derivedtherefrom as an ADC input signal, and wherein the ADC is configured toperform an analog-to-digital (A/D) conversion of the ADC input signal toderive the digital BB signal; a first feedback path configured tofeedback the filtered analog BB signal to the ABB filter stage; and asecond feedback path configured to feedback the digital BB signal to theABB filter stage, wherein the second feedback path comprises a firstfeedback digital-to-analog (D/A) converter.
 2. The receiver according toclaim 1, wherein the first feedback path or the second feedback path isswitchable; or the first feedback path and the second feedback path areswitchable.
 3. The receiver according to claim 2, wherein the receiveris configured to selectively switch on and switch off the first feedbackpath and the second feedback path in response to a signal type of thereceived analog BB signal.
 4. The receiver according to claim 1, whereinthe second feedback path comprises a delay element.
 5. The receiveraccording to a claim 1, wherein the ABB filter stage comprises a firstsummation node, a first integrator, a second summation node and a secondintegrator; wherein the first summation node is configured to receivethe analog BB signal and the filtered analog BB signal from the firstfeedback path, and to provide a first sum signal to the firstintegrator; wherein the first integrator is configured to integrate thefirst sum signal to derive a first integrated signal; wherein the secondsummation node is configured to receive the first integrated signal andthe digital BB signal from the second feedback path, and to provide asecond sum signal to the second integrator; wherein the secondintegrator is configured to integrate the second sum signal to derivethe filtered analog BB signal.
 6. The receiver according to claim 5,wherein the ADC stage comprises a third integrator coupled between theADC stage input and the ADC input.
 7. The receiver according to claim 6,wherein the ADC stage comprises a third summation node at the ADC stageinput and a third feedback path, wherein the third feedback path isconfigured to feed back the digital BB signal to the third summationnode, wherein the third feedback path comprises a second feedback D/Aconverter, and wherein the third summation node is configured to sum thedigital BB signal from the third feedback path and the filtered analogBB signal and to provide a resulting third sum signal to the thirdintegrator.
 8. The receiver according to claim 5, wherein the ABB filterstage comprises a fourth feedback path connected between a firstintegrator output of the first integrator and the first summation node.9. The receiver according to claim 5, further comprising a fifthfeedback back path configured to feedback the filtered analog BB signalto the first summation node.
 10. The receiver according to claim 9,wherein at least one of the first feedback path, the second feedbackpath, the third feedback path, the fourth feedback path, or the fifthfeedback path is switchable.
 11. The receiver according to claim 10,wherein the receiver is configured to selectively switch on and switchoff the first to fifth feedback paths in response to a signal type ofthe received analog BB signal.
 12. A communication device for a wirelesscommunication system, the communication device comprising a receivercomprising: an analog baseband (ABB) filter stage including an ABBfilter stage input configured to receive an analog baseband (BB) signaland an ABB filter stage output configured to provide a filtered analogBB signal; an analog-to-digital converter (ADC) stage, including: an ADCstage input configured to receive the filtered analog BB signal and anADC stage output configured to provide a digital BB signal; and an ADCcomprising an ADC input configured to receive the filtered analog BBsignal or a signal derived therefrom as an ADC input signal, and whereinthe ADC is configured to perform an analog-to-digital (A/D) conversionof the ADC input signal to derive the digital BB signal; a firstfeedback path configured to feedback the filtered analog BB signal tothe ABB filter stage; and a second feedback path configured to feedbackthe digital BB signal to the ABB filter stage, wherein the secondfeedback path comprises a first feedback digital-to-analog (D/A)converter.
 13. The communication device of claim 12, wherein the firstfeedback path or the second feedback path is switchable; or the firstfeedback path and the second feedback path are switchable.
 14. Thecommunication device of claim 13, wherein the receiver is configured toselectively switch on and switch off the first feedback path and thesecond feedback path in response to a signal type of the received analogBB signal.
 15. The communication device of claim 12, wherein the secondfeedback path comprises a delay element.
 16. The communication device ofclaim 12, wherein the ABB filter stage comprises a first summation node,a first integrator, a second summation node and a second integrator,wherein the first summation node is configured to receive the analog BBsignal and the filtered analog BB signal from the first feedback path,and to provide a first sum signal to the first integrator, wherein thefirst integrator is configured to integrate the first sum signal toderive a first integrated signal, wherein the second summation node isconfigured to receive the first integrated signal and the digital BBsignal from the second feedback path, and to provide a second sum signalto the second integrator, wherein the second integrator is configured tointegrate the second sum signal to derive the filtered analog BB signal.17. The communication device of claim 16, wherein the ADC stagecomprises a third integrator coupled between the ADC stage input and theADC input.
 18. The communication device of claim 17, wherein the ADCstage comprises a third summation node at the ADC stage input and athird feedback path, wherein the third feedback path is configured tofeed back the digital BB signal to the third summation node, wherein thethird feedback path comprises a second feedback D/A converter, andwherein the third summation node is configured to sum the digital BBsignal from the third feedback path and the filtered analog BB signaland to provide a resulting third sum signal to the third integrator.